Semiconductor charge pump using MOS (metal oxide semiconductor) transistor for current rectifier device

ABSTRACT

A semiconductor charge pump includes a plurality of P-channel MOS transistors being connected in series, a plurality of first pumping capacitors one electrode of each of which is connected to a connection point of each of the P-channel MOS transistors, a clock signal generating circuit which generates first and second clock signals whose phases are different from each other by 180 degrees, the first and second clock signals being alternately supplied to the other electrodes of the first pumping capacitors. The semiconductor charge pump further includes a plurality of dynamic level converter circuits each including a resistor element and a second pumping capacitor and connected to each of gates of the P-channel MOS transistors.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a divisional application of and claims the benefitof priority under 35 USC §120 of application Ser. No. 12/138,005, filedon Jun. 12, 2008, now U.S. Pat. No. 7,532,062, which is a divisional ofSer. No. 11/556,810, filed on Nov. 6, 2006, now abandoned, and claimsthe benefit of priority under 35 USC §119 from Japanese PatentApplications No. 2005-323601, filed Nov. 8, 2005; and No. 2006-266050,filed Sep. 28, 2006, the entire contents of each of which areincorporated herein by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a semiconductor charge pump, and moreparticularly to a Dickson type voltage increasing charge pump using MOStransistors for a current rectifier element.

2. Description of the Related Art

In recent years, there has been prevalent a nonvolatile semiconductormemory device featured in that even if power is down, no information islost. In particular, there is a high demand for such a nonvolatilesemiconductor memory device in management of information relating toredundancy of memory devices or maintaining chip specific information, atrimming process of an analog circuit, a speed matching process of ahigh speed computation logic or the like. Common requests for thenonvolatile semiconductor memory device in these uses include that amemory capacity may be about several thousands bits at most (may besmall in size); that there is no need for rewriting information as longas it has been written once; that packaging on chip is inexpensive orthe like. Namely, there has been a request for “inexpensively packaginga small-scale nonvolatile semiconductor memory device on the same chip”.

An irreversible nonvolatile semiconductor memory device using a fuseelement for a memory element meets such a request. However, theconventional fuse element has been formed so as to thermally weld awiring layer by means of laser irradiation. Therefore, the nonvolatilesemiconductor memory device using a fuse element of this type has adisadvantage that information cannot be written after chip sealing(packaging) has been done.

In contrast, recently, a so called gate oxide film destruction typeanti-fuse element has been used as a memory element for a nonvolatilesemiconductor memory device formed to apply a high voltage to a gateoxide film of a MOS transistor and utilize a breakdown phenomenon of anoxidization insulation film. In the case of this irreversiblenonvolatile semiconductor memory device using the anti-fuse element, itis possible to write information after sealing.

On the other hand, in terms of the nonvolatile semiconductor memorydevice, there is well known a nonvolatile semiconductor memory devicecapable of electrically erasing information. A nonvolatile semiconductormemory device of this type includes: a Flash EPROM (ElectricallyProgrammable Read Only Memory); an MRAM (Magnetic Random Access Memory);and a FeRAM (Ferroelectric Random Access Memory). In the case of thenonvolatile semiconductor memory device of this type, specific memoryelements are used, respectively, in order to package a number oflarge-scale memory elements in a small area. However, a dedicatedmanufacturing process is necessary for forming specific memory elements.The use of the dedicated manufacturing process increases a manufacturingcost. In addition, the use of the dedicated manufacturing process causesthe following problems. For example, the above use of the process causesdegradation of memory characteristics of other memory elements packaged,respectively, on the same chip; increases characteristic degradation orcharacteristic variation of an analog circuit element; and causes speedcharacteristic degradation of transistors for a high speed computationlogic. Therefore, the request for “inexpensively packaging a small-scalenonvolatile semiconductor memory device on the same chip” is notsatisfied in the case of such a nonvolatile semiconductor memory devicecapable of electrically erasing information.

A specific manufacturing process is not required to form a memoryelement in the case of the above-described irreversible nonvolatilesemiconductor memory device using a gate oxide film destruction typeanti-fuse element. Thus, this memory device is suitable for a requestfor “inexpensively packaging a small-scale nonvolatile semiconductormemory device on the same chip”. However, an information write operationrequires a high voltage. Therefore, in order to ensure packaging on thesame chip, it is indispensable to achieve means for supplying a highvoltage.

The simplest high voltage supply means can include a configuration suchthat high voltage power is supplied from the outside of the chip via anexternal supply pin. With this configuration, there is a danger thatelectrostatic breakdown of a fuse element occurs due to electrostaticapplication to the external supply pin. Thus, it is necessary toadditionally provide a protective element to the external supply pin forprotecting the fuse element from electrostatic breakdown. However, thisconfiguration must meet a contradictory specification such that itpermits high voltage application for storing information in the fuseelement, whereas it prevents high voltage (electrostatic) applicationthat causes electrostatic breakdown of the fuse element. Therefore, itis not permissible to additionally provide the protective element to theexternal supply pin. This makes it impossible to utilize an advantage ofa gate oxide film destruction type anti-fuse element that informationcan be written after sealing.

Another means for supplying a high voltage can include a configurationsuch that a voltage increase power source such as a Dickson type chargepump is packaged on the same chip (for the Dickson type charge pump,reference should be made to J. F. Dickson, “On-chip high-voltagegeneration in MNOS integrated circuits using an improved voltagemultiplier technique,” IEEE J. Solid-State Circuits, vol. SC-11, pp.374-378, June 1976.) However, specific elements such as diodes and highwithstand voltage transistors are required to configure the Dickson typecharge pump. However, requiring such specific elements reduces anattraction attained by using a gate oxide film destruction typeanti-fuse element that does not require a specific manufacturing processfor a nonvolatile semiconductor memory device.

For example, in the Dickson type charge pump in which five currentrectifier elements have been connected in series, a diode having a dualwell structure is indispensable as a current rectifier element in orderto normally operate this charge pump. This is because, if a parasiticdiode is used for the current rectifier element that configures theDickson type charge pump, when a PN junction of the parasitic diode isbiased in a forward direction, for example, a PNP parasitic bipolarcomposed of a P+ type diffusion layer being an anode terminal, an N-typewell being a cathode terminal, and a P-type substrate becomeselectrically conductive. Therefore, a current charged from the anodeterminal leaks onto the P-type substrate, and the charge pump does notfunction normally. In contrast, if a diode having a dual well structureis used for the current rectifier element that configures the Dicksontype charge pump, all electrons being minority carriers charged from anN+ type diffusion layer serving as a cathode terminal are collected tothe anode terminal without any leak to another node. Therefore, thecharge pump functions normally. However, the diode having the dual wellstructure is high in its manufacturing cost, as compared with that ofthe parasitic diode. In this case, even if there has been used a gateoxide film destruction type anti-fuse element that does not require aspecific manufacturing process, an inexpensive nonvolatile semiconductormemory device cannot be provided.

In the Dickson type charge pump, there has been reported a configurationin which diode-connected N-channel MOS transistors are used as currentrectifier elements, and these elements are connected in series. (Forexample, reference should be made to Toru Tanzawa and Tomoharu Tanaka,“A Dynamic Analysis of the Dickson Charge Pump Circuit”, IEEE Journal ofsolid-state circuits, vol. 32, No. 8, August 1997, pp. 1231-1240).However, in the case of this Dickson type charge pump, a back gateeffect of rectification characteristics of the diode-connected N-channelMOS transistors becomes a problem. The back gate effect used heredenotes that a voltage (threshold voltage), at which a current startsflowing between a source and a drain, becomes high in accordance withthe increase in back gate voltage. In the case where an N-channel MOStransistor having such rectification characteristics has been used as acurrent rectifier element, a current drive capability is lowered as avoltage-increase voltage of the Dickson type charge pump becomes high,and finally, no current flows. Thus, even in the Dickson type chargepump composed of diode-connected N-channel MOS transistors, it has beenimpossible to provide an inexpensive nonvolatile semiconductor memorydevice using a gate oxide film destruction type anti-fuse element.

BRIEF SUMMARY OF THE INVENTION

According to a first aspect of the present invention, there is provideda semiconductor charge pump comprising: a plurality of P-channel MOS(Metal Oxide Semiconductor) transistors which configure currentrectifier elements, respectively, said plurality of P-channel MOStransistors having gates and being connected in series between anexternal supply power source and a voltage increase output power source;a plurality of first pumping capacitors one electrode of each of whichis connected to a connection point of each of said plurality ofP-channel MOS transistors; a clock signal generating circuit whichgenerates first and second clock signals whose phases are different fromeach other by 180 degrees, the first and second clock signals beingalternately supplied from the clock signal generating circuit to theother electrodes of said plurality of first pumping capacitors; aplurality of resistor elements connected to connection points of saidplurality of P-channel MOS transistors at one end and connected to gatesof said plurality of P-channel MOS transistors at the other end; and aplurality of second pumping capacitors one electrode of each of which isconnected to the other end of each of said plurality of resistorelements, the first and second clock signals being alternately suppliedto the other electrodes of said plurality of second pumping capacitors,thereby generating control signals which control gates of said pluralityof P-channel MOS transistors.

According to a second aspect of the present invention, there is provideda semiconductor charge pump comprising: a plurality of N-channel MOS(Metal Oxide Semiconductor) transistors which configure currentrectifier elements, respectively, said plurality of N-channel MOStransistors having gates and being connected in series between anexternal supply power source and a voltage increase output power source;a plurality of first pumping capacitors one electrode of each of whichis connected to a connection point of each of said plurality ofN-channel MOS transistors; a clock signal generating circuit whichgenerates first and second clock signals whose phases are different fromeach other by 180 degrees, the first and second clock signals beingalternately supplied from the clock signal generating circuit to theother electrodes of said plurality of first pumping capacitors; aplurality of resistor elements connected to connection points of saidplurality of N-channel MOS transistors at one end and connected to gatesof said plurality of N-channel MOS transistors at the other end; and aplurality of second pumping capacitors one electrode of each of which isconnected to the other end of each of said plurality of resistorelements, the first and second clock signals being alternately suppliedto the other electrodes of said plurality of second capacitors, therebygenerating control signals which control gates of said plurality ofN-channel MOS transistors.

According to a third aspect of the present invention, there is provideda semiconductor charge pump for two systems, comprising: a plurality ofP-channel MOS (Metal Oxide Semiconductor) transistors which configurecurrent rectifier elements, respectively, said plurality of P-channelMOS transistors having gates and being connected in series between anexternal supply power source and a voltage increase output power source;a plurality of first pumping capacitors one electrode of each of whichis connected to a connection point of each of said plurality ofP-channel MOS transistors; a clock signal generating circuit whichgenerates first and second clock signals whose phases are different fromeach other by 180 degrees, the first and second clock signals beingalternately supplied from the clock signal generating circuit to theother electrodes of said plurality of first pumping capacitors; aplurality of resistor elements connected to connection points of saidplurality of P-channel MOS transistors at one end and connected to gatesof said plurality of P-channel MOS transistors at the other end; and aplurality of second pumping capacitors one electrode of each of which isconnected to the other end of each of said plurality of resistorelements, the first and second clock signals being alternately suppliedto the other electrodes of said plurality of second pumping capacitors,thereby generating control signals which control gates of said pluralityof P-channel MOS transistors, wherein, by means of the control signalgenerated by said plurality of second pumping capacitors in thesemiconductor charge pump for one system, gates of said plurality ofP-channel MOS transistors in the semiconductor charge pump for the othersystem are controlled.

According to a fourth aspect of the present invention, there is provideda semiconductor charge pump for two systems, comprising: a plurality ofN-channel MOS (Metal Oxide Semiconductor) transistors which configurecurrent rectifier elements, respectively, said plurality of N-channelMOS transistors having gates and being connected in series between anexternal supply power source and a voltage increase output power source;a plurality of first pumping capacitors one electrode of each of whichis connected to a connection point of each of said plurality ofN-channel MOS transistors; a clock signal generating circuit whichgenerates first and second clock signals whose phases are different fromeach other by 180 degrees, the first and second clock signals beingalternately supplied from the clock signal generating circuit to theother electrodes of said plurality of first pumping capacitors; aplurality of resistor elements connected to connection points of saidplurality of N-channel MOS transistors at one end and connected to gatesof said plurality of N-channel MOS transistors at the other end; and aplurality of second pumping capacitors one electrode of each of which isconnected to the other end of each of said plurality of resistorelements, the first and second clock signals being alternately suppliedto the other electrodes of said plurality of second pumping capacitors,thereby generating control signals which control gates of said pluralityof N-channel MOS transistors, wherein, by means of the control signalgenerated by said plurality of second pumping capacitors in thesemiconductor charge pump for one system, gates of said plurality ofN-channel MOS transistors in the semiconductor charge pump for the othersystem are controlled.

BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWING

FIG. 1 is a circuit diagram depicting an example of a configuration ofan irreversible nonvolatile semiconductor memory device using a gateoxide film destruction type anti-fuse element, according to the presentinvention;

FIG. 2 is a circuit diagram depicting an example of a configuration of aDickson type charge pump (voltage increase charge pump) suitable for usein the irreversible nonvolatile semiconductor memory device according toa first embodiment of the present invention;

FIGS. 3A to 3E are waveform diagrams each adapted to explain anoperation of the Dickson type charge pump shown in FIG. 2;

FIG. 4 is a circuit diagram depicting another example of a configurationof a Dickson type charge pump for comparison with the Dickson typecharge pump shown in FIG. 2;

FIG. 5 is a circuit diagram depicting still another example of aconfiguration of a Dickson type charge pump for comparison with theDickson type charge pump shown in FIG. 2;

FIG. 6 is a circuit diagram depicting an example in which the Dicksontype charge pump shown in FIG. 2 is configured as a negative chargepump;

FIG. 7 is a circuit diagram depicting an example of a configuration of aDickson type charge pump (voltage increase charge pump) suitable for usein the irreversible nonvolatile semiconductor memory device according toa second embodiment of the present invention;

FIG. 8 is a circuit diagram depicting an example of a configuration of acharge pump (voltage increase charge pump) suitable for use in theirreversible nonvolatile semiconductor memory device according to athird embodiment of the present invention;

FIGS. 9A to 9E are waveform diagrams each adapted to explain anoperation of the charge pump shown in FIG. 8;

FIG. 10 is a circuit diagram depicting an example of a configuration ofa charge pump (voltage increase charge pump) suitable for use in theirreversible nonvolatile semiconductor memory device according to afourth embodiment of the present invention;

FIG. 11 is a circuit diagram depicting an example of a configuration ofa charge pump (voltage increase charge pump) suitable for use in theirreversible nonvolatile semiconductor memory device according to afifth embodiment of the present invention; and

FIG. 12 is a circuit diagram depicting an example of a configuration ofa charge pump (voltage increase charge pump) suitable for use in theirreversible nonvolatile semiconductor memory device according to asixth embodiment of the present invention.

DETAILED DESCRIPTION OF THE INVENTION

Embodiments of the present invention will be described with reference tothe accompanying drawings. It should be noted that the drawings areschematic ones and the dimension ratios shown therein are different fromthe actual ones. The dimensions vary from drawing to drawing and so dothe ratios of dimension. The following embodiments are directed to adevice and a method for embodying the technical concept of the presentinvention and the technical concept does not specify the material,shape, structure or configuration of components of the presentinvention. Various changes and modifications can be made to thetechnical concept without departing from the scope and the claimedinvention.

First Embodiment

FIG. 1 shows a basic configuration of a nonvolatile semiconductor memorydevice using a voltage increase charge pump (described later) inaccordance with a first embodiment of the present invention. The presentembodiment describes an example of an irreversible nonvolatilesemiconductor memory device using a gate oxide film destruction typeanti-fuse element as a memory element, featured in that informationrewriting is impossible. This nonvolatile semiconductor memory device isprovided as an example in which the number of fuse elements is “4”.

For example, data input signals DI <0> to DI <3> are supplied to oneinput ends of write control logic circuits (AND circuits) 11 a to 11 d,respectively. A write control signal WTITE (=1) supplied from theoutside of the device is inputted to the other input end of each of thewrite control logic circuits 11 a to 11 d at the time of a writeoperation. Output ends of the write control logic circuits 11 a to 11 dare connected to gates of write control switches 12 a to 13 d,respectively. The write control switches 12 a to 12 d each consist ofN-channel MOS transistors (hereinafter, referred to as N-type MOStransistors).

One of the source and the drain of each of the above write controlswitches 12 a to 12 d (for example, source) is grounded. The other oneof the source and the drain of the write control switches 12 a to 12 d(for example, drain) is connected to one terminal (each gate) of each ofgate oxide film destruction type anti-fuse elements 13 a to 13 d. Thegate oxide film destruction type anti-fuse elements 13 a to 13 d eachconsist of P-channel MOS transistors (hereinafter, referred to as P-typeMOS transistors). One of the source and the drain of a readout powersupply circuit (N-type MOS transistor) 14 (for example, source) and avoltage increase charge pump 15 serving as an internal voltage increasepower source each are connected to the other terminal (source, drain, orback gate) of each of the gate oxide film destruction type anti-fuseelements 13 a to 13 d.

An oscillator 16 is connected to the voltage increase charge pump 15.The above write control signal WRITE (high level “=1”) is supplied fromthe outside of the device to the oscillator 16 at the time of a writeoperation. That is, at the time of the write operation, a clock signal Φaccording to the write control signal WRITE (=1) is outputted from theabove oscillator 16 to the above voltage increase charge pump 15. Inthis manner, a voltage increase output power source (electric potential)VPP according to the clock signal (is generated by means of the voltageincrease charge pump 15. This voltage increase output power source VPPis applied to the source, drain, and back gate of the gate oxide filmdestruction type anti-fuse elements 13 a to 13 d, respectively.

An external supply power source VDD is supplied to the other one (drain)of the source and the drain of the above readout power supply circuit14. A readout control signal READ (=1) is supplied from the outside ofthe device to the gate of the above readout power supply circuit 14 atthe time of a readout operation.

The above readout control signal READ (=1) is supplied to each of thegates of readout load circuits (N-type MOS transistors) 17 a to 17 d.One of the source and the drain of each of the readout load circuits 17a to 17 d (for example, source) is grounded via each of resistors 18 ato 18 d, respectively. The other one of the source and the drain of eachof the readout load circuits 17 a to 17 d (for example, drain) isconnected to each connection point between each of the write controlswitches 12 a to 12 d and each of the gate oxide film destruction typeanti-fuse elements 13 a to 13 d.

In addition, non-inverting input end of each of differential amplifiers19 a to 19 d is connected to each connection point between each of thewrite control switches 12 a to 12 d and each of the gate oxide filmdestruction type anti-fuse elements 13 a to 13 d. A reference powersource VREF is supplied from the outside of the device to an invertinginput end of each of the differential amplifiers 19 a to 19 d at thetime of a readout operation. Data output signals DO <0> to DO <3> areoutputted from output ends of these differential amplifiers 19 a to 19d, respectively.

In such a configuration, “1” and “0” are provided as a write controlsignal WRITE and a readout control signal READ, respectively, at thetime of a write operation. Then, the oscillator 16 is activated by meansof the write control signal WRITE, and then, outputs the clock signal Φ.The voltage increase charge pump 15 having received that clock signal Φvoltage-increases the voltage increase output power source VPP. Thisvoltage increase output power source VPP is applied to the otherterminal of each of the gate oxide film destruction type anti-fuseelements 13 a to 13 d.

In the case where data input signals D1 <0>, DI <1>, DI <2>, and DI <3>each are set to “1”, each of the outputs of the write control logiccircuits 11 a to 11 d is set to “1”. In this manner, the write controlswitches 12 a to 12 d become electrically conductive. Then, a highvoltage stress (voltage increase output power source VPP) is appliedfrom the voltage increase charge pump 15 to the gate oxide filmdestruction type anti-fuse elements 13 a to 13 d. By maintaining thisstate, the gate oxide film of the anti-fuse elements 13 a to 13 d thenbreaks down, and is thermally destructed by a current that flows there.The thermally destructed gate oxide film flows a current, although it isweak. Namely, in the irreversible nonvolatile semiconductor memorydevice, information is stored while the state in which the gate oxidefilm has been thermally destructed is set to “1” and a good insulationstate before the destruction is set to “0”. The thus thermallydestructed gate oxide film does not return to its original goodinsulation state again.

On the other hand, at the time of a readout operation, “1” is providedas a readout control signal READ, and “0” is provided as a write controlsignal WRITE. Then, the readout load circuits 17 a to 17 d and thereadout power supply circuit 14 become electrically conductive. In thismanner, the external supply power source VDD is supplied to the otherterminal of each of the gate oxide film destruction type anti-fuseelements 13 a to 13 d. The external supply power source VDD is, forexample, about 1.2V that is a voltage required to read out informationfrom the anti-fuse elements 13 a to 13 d.

In this case, an anti-fuse element in which no information is written isestablished in an insulation state, and thus, no current flows. Acurrent flows only in an anti-fuse element in which information has beenwritten. The current flowing in the anti-fuse elements 13 a to 13 d isdetected by means of the readout load circuits 17 a to 17 d. Namely, anelectric potential difference according to the flowing current quantityoccurs in the readout load circuits 17 a to 17 d. The electricalpotential difference is compared with a reference power supply VREF bymeans of the differential amplifiers 19 a to 19 d. In this manner, it isjudged whether or not information is written into the anti-fuse elements13 a to 13 d.

Hereinafter, a specific description will be given with respect to aconfiguration of a Dickson type charge pump suitable for use as avoltage increase charge pump in a nonvolatile semiconductor memorydevice having a configuration shown in FIG. 1.

FIG. 2 shows an example of a configuration of a Dickson type charge pumpin accordance with the first embodiment of the present invention. Thepresent embodiment describes an example in which P-type MOS transistorsare used as current rectifier elements and five P-type MOS transistorsare connected in series.

As shown in FIG. 2, five P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15₋₄, and 15 ₋₅ are connected in series between the external supply powersource VDD and the voltage increase output power supply VPP. Oneelectrode of each of pumping capacitors (first pumping capacitors) Ca1,Ca2, Ca3, and Ca4 is connected to each one of nodes V1, V2, V3, and V4serving as serial connection points of the above P-type MOS transistors15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅

Two clock signals Φ1 and Φ2 each having a phase difference of 180degrees are alternately supplied from a clock signal generating circuit15 a to the other electrode of each of the above pumping capacitors Ca1,Ca2, Ca3, and Ca4. That is, among the above pumping capacitors Ca1, Ca2,Ca3, and Ca4, for example, the first clock signal Φ2 from a first clocksignal generator unit 15 a ₋₁ is applied to the other electrode of eachof the pumping capacitors Ca2 and Ca4. In addition, for example, thesecond clock signal Φ2 from a second clock signal generator unit 15 a ₋₂is applied to the other electrode of each of the pumping capacitors Ca1and Ca3.

The first and second clock signal generator units 15 a ₋₁ and 15 a ₋₂each are composed of an inverter circuit having a complementary MOS(CMOS) structure. The first clock signal Φ1 is generated based on theclock signal Φ from the above oscillator 16. The second clock signal Φ2is generated based on the clock signal Φ1. The first and second clocksignals Φ1 and Φ2 each have a phase difference of 180 degrees.

On the other hand, dynamic level converter circuits 15 b ₋₁, 15 b ₋₂, 15b ₋₃, 15 b ₋₄, and 15 b ₋₅ are connected to gates of the above P-typeMOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively. Thedynamic level converter circuits 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and15 b ₋₅ are composed of resistor elements R1, R2, R3, R4, and R5 andauxiliary pumping capacitors (second pumping capacitors) Cb1, Cb2, Cb3,Cb4, and Cb5, respectively. One ends of the resistor elements R1, R2,R3, R4, and R5 are connected to nodes V1, V2, V3, and V4 of the aboveP-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅; and a nodeV5 between the P-type MOS transistor 15 ₋₅ and the voltage increaseoutput power source VPP. The other ends of the resistor elements R1, R2,R3, R4, and R5 are connected to the gates of the above P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, and also connected toone electrodes of the auxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4,and Cb5, respectively. The first and second clock signals Φ1 and Φ2 fromthe above clock signal generating circuit 15 a are alternately suppliedto the other electrodes of the auxiliary pumping capacitors Cb1, Cb2,Cb3, Cb4, and Cb5.

That is, the dynamic level converter circuits 15 b ₋₁, 15 b ₋₂, 15 b ₋₃,15 b ₋₄, and 15 b ₋₅ branch a current from the nodes V1, V2, V3, V4, andV5, respectively, via the resistor elements R1, R2, R3, R4, and R5. Inaddition, an electric charge obtained by each branched current is storedin each of the auxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5.In this state, the other electrode of each of the auxiliary pumpingcapacitors Cb1, Cb2, Cb3, Cb4, and Cb5 is alternately driven by means ofthe above first or second clock signal Φ1 or Φ2. In this manner, gatesignals (control signals) G1, G2, G3, G4, and G5 of intermediateelectric potentials of desired electric potentials, for example, gatevoltages, for controlling the gates of the P-type MOS transistors 15 ₋₁,15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, are generated.

Now, with reference to FIGS. 3A to 3E, a description will be given withrespect to an operation of the voltage increase charge pump 15 havingthe configuration described above. Here, FIGS. 3A to 3E each show arelationship among: outputs (gate signals) G1, G2, G3, G4, and G5 of thedynamic level converter circuits 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and15 b ₋₅; electric potentials of the nodes V1, V2, V3, and V4; theexternal supply power source VDD; and the voltage increase output powersource VPP. Each horizontal axis denotes a time (t), and each verticalaxis denotes an electric potential (V).

As shown in FIGS. 3A to 3E, in a period phase 1, the outputs G1, G3, andG5 of the dynamic level converter circuits 15 b ₋₁, 15 b ₋₃, and 15 b ₋₅become low electric potentials. In this manner, the P-type MOStransistors 15 ₋₁, 15 ₋₃, and 15 ₋₅ whose gates are controlled by meansof the outputs G1, G3, and G5 each enter an ON state. Then, the electricpotentials at both ends of each of the P-type MOS transistors 15 ₋₁, 15₋₃, and 15 ₋₅ (between the external supply power source VDD and the nodeV1, between the node V2 and the node V3, and between the node V4 and thevoltage increase output power source VPP) become identical to eachother. At this time, the outputs G2 and G4 of the other dynamic levelconverter circuits 15 b ₋₂ and 15 b ₋₄ become high electric potentials.In this manner, the P-type MOS transistors 15 ₋₂ and 15 ₋₄ whose gatesare controlled by means of the outputs G2 and G4 each are in an OFFstate. Therefore, the electric potential of the node V1 is convergedinto that of the external supply power source VDD. In addition, theelectric potentials of the nodes V2 and V3 are converged into theelectric potential determined by redistribution of the electric chargesstored in the pumping capacitors Ca2 and Ca3. In addition, the electricpotentials of the node V4 and the voltage increase output power sourceVPP are converged into the electric potential determined byredistribution of the electric charges stored in the pumping capacitorCa4 and a load capacity (not shown) of the voltage increase output powersource VPP connected to the node V4.

On the other hand, in a period phase 2, the outputs G2 and G4 of thedynamic level converter circuits 15 b ₋₂ and 15 b ₋₄ become low electricpotentials. In this manner, the P-type MOS transistors 15 ₋₂ and 15 ₋₄whose gates are controlled by means of the outputs G2 and G4 each enteran ON state. Then, the electric potentials at both ends of each of theP-type MOS transistors 15 ₋₂ and 15 ₋₄ (between the node V1 and the nodeV2 and between the node V3 and the node V4) become identical to eachother. At this time, the outputs G1, G3, and G5 of the other dynamiclevel converter circuits 15 b ₋₁, 15 b ₋₃, and 15 b ₋₅ become highelectric potentials. In this manner, the P-type MOS transistors 15 ₋₁,15 ₋₃, and 15 ₋₅ whose gates are controlled by the outputs G1, G3, andG5 each enter an OFF state. Therefore, the electric potentials of thenodes V1 and V2 are converged into the electric potential determined byredistribution of the electric charges stored in the pumping capacitorsCa1 and Ca2. In addition, the electric potentials of the nodes V3 and V4are converged into the electric potential determined by redistributionof the electric charges stored in the pumping capacitors Ca3 and Ca4.

In this way, by repeating operations of the above periods phase 1 andphase 2, the electric charge is sequentially transferred to the voltageincrease output power source VPP from the external power supply sourceVDD through the pumping capacitors Ca1, Ca2, Ca3, and Ca4. This isidentical to a basic operation of a voltage increase function of aDickson type charge pump.

Now, a description will be given with respect to electricalcharacteristics required for an internal voltage increase power source,the electrical characteristics being required to utilize a MOStransistor manufactured for a 1.2V power source as an anti-fuse elementby destructing its gate oxide film. With respect to the requiredelectrical characteristics, a voltage (voltage increase capacity) of thevoltage increase output power source VPP required to write informationis about 6V (volts), and the current drive capability at the time ofoutput of 5V is about 2 mA (milliamperes) (in the case of the latest 90nm (nanometers) technology (design rule) generation). In the case of aDickson type charge pump (15) shown in the first embodiment, a voltageincrease output electric potential VPP on the order of 6V can beobtained by supplying an external supply power source VDD of 2.5V. Inaddition, assuming that the capacitance of each of the pumpingcapacitors Ca1, Ca2, ca3, and Ca4 is 4 pF (pico-Farads) and that afrequency of a clock signal Φ is 400 MHz (mega-hertz), the current drivecapability on the order of 2 mA can be obtained at the time of output of5V. At this time, the resistance values of the resistor elements R1, R2,R3, R4, and R5 that configure the dynamic level converter circuits 15 b₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and 15 b ₋₅, respectively, are properlyon the order of 15 KΩ (kilo-ohms) and the capacitance values of theauxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5 are properly onthe order of 1 pF, respectively.

As described above, it is preferable that the Dickson type charge pumpshown in the first embodiment (refer to FIG. 2) be used as an internalvoltage increase power source (voltage increase charge pump 15) of anirreversible nonvolatile semiconductor memory device using a gate oxidefilm destruction type anti-fuse element.

In addition, in the first embodiment, a source-drain voltage and asource-gate voltage applied to all of the transistors configuring theDickson type charge pump are equal to or smaller than the externalsupply power source VDD. Therefore, if the external supply power sourceVDD is 2.5V, element reliability can be fully obtained by using generaltransistors configuring an input/output buffer. Namely, according to thefirst embodiment, the Dickson type charge pump can be configured withoutany need for a specific element (for example, high withstand voltage MOStransistor) or a specific manufacturing process. Therefore, anirreversible nonvolatile semiconductor memory device using a gate oxidefilm destruction type anti-fuse element (refer to FIG. 1) can beinexpensively provided.

Now, a description will be given in more detail with respect to acontrivance for improving a current drive capability or the like in aDickson type charge pump (15) using a P-type MOS transistor as a currentrectifier element.

FIG. 4 shows another example of a configuration of a Dickson type chargepump. This Dickson type charge pump is shown for the purpose ofcomparison with the Dickson type charge pump in accordance with thefirst embodiment of the present invention shown in FIG. 2, with respectto enhancement (improvement) of the current drive capability in the casewhere a P-type MOS transistor is used as a current rectifier element.

That is, this Dickson type charge pump 150 is configured so that onediode-connected N-type MOS transistor 150 ₋₁ and four diode-connectedP-type MOS transistors 150 ₋₂, 150 ₋₃, 150 ₋₄, and 150 ₋₅ are connectedin series. One electrodes of the pumping capacitors C1, C2, C3, and C4are connected to the nodes V1, V2, V3, and V4 of the N-type transistor150 ₋₁ and the P-type MOS transistors 150 ₋₂, 150 ₋₃, 150 ₋₄, and 150₋₅, respectively. The first or second clock signal Φ1 or Φ2 from theclock signal generating circuit 15 a is alternately supplied to theother electrode of each of the pumping capacitors C1, C2, C3, and C4.

In addition, a power source VSS at a low electric potential side issupplied to a back gate of the above N-type MOS transistor 150 ₋₁. Backgate bias circuits 151 ₋₁, 151 ₋₂, 151 ₋₃, and 151 ₋₄ are connected toback gates of the P-type MOS transistors 150 ₋₂, 150 ₋₃, 150 ₋₄, and 150₋₅, respectively. The back gate bias circuits 151 ₋₁, 151 ₋₂, 151 ₋₃,and 151 ₋₄ each bias an N-well (not shown) that is a back gate of eachof the P-type MOS transistors 150 ₋₂, 150 ₋₃, 150 ₋₄, and 150 ₋₅ at anintermediate electric potential of a back gate voltage in the case wherethe above P-type MOS transistors 150 ₋₂, 150 ₋₃, 150 ₋₄, and 150 ₋₅ areformed on a P-type substrate (not shown). The back gate bias circuits151 ₋₁, 151 ₋₂, 151 ₋₃, and 151 ₋₄ are configured such that two P-typeMOS transistors 151 a and 151 b are connected in series between each ofthe nodes V1, V2, V3, V4 and the node V5 between the P-type MOStransistor 150 ₋₅ and the voltage increase output power source VPP.

In the case where such a configuration is provided, the back gates ofthe P-type MOS transistors 150 ₋₂, 150 ₋₃, 150 ₋₄, and 150 ₋₅ can bebiased at an intermediate electric potential of a back gate voltage bymeans of the back gate bias circuits 151 ₋₁, 151 ₋₂, 151 ₋₃, and 151 ₋₄.Therefore, the influence of a back gate effect generated by the N-typeMOS transistor, as described previously, can be avoided.

However, the current drive capability of the P-type MOS transistor islow, i.e., equal to or smaller than ½ as compared with the current drivecapability of the N-type MOS transistor. Namely, the current drivecapability of the Dickson type charge pump using the P-type MOStransistor is remarkably low. In the case where an attempt is made toobtain the current drive capability equal to that of the Dickson typecharge pump using the N-type MOS transistor, it is necessary to increasean element size and to have a chip area of at least twice as large asusual. Moreover, a parasitic capacitance increases as the element sizeincreases, and a charge/discharge current relevant to its parasiticcapacitance increases. Therefore, the voltage increase capability of theDickson type charge pump is extremely lowered. In this way, the voltageincrease capability and the current drive capability become insufficientin the Dickson type charge pump configured by diode-connecting theP-type MOS transistors. Therefore, an irreversible nonvolatilesemiconductor memory device using a gate oxide film destruction typeanti-fuse element cannot be provided.

In contrast, in the case of the Dickson type charge pump (15) inaccordance with the first embodiment of the present invention shown inFIG. 2, the intermediate electric potentials (gate signals G1, G2, G3,G4, and G5) of the gate voltages for controlling gates of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ are generated by meansof the dynamic level converter circuits 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b₋₄, and 15 b ₋₅. In this manner, even in the Dickson type charge pumpusing the P-type MOS transistor, it becomes possible to improve thevoltage increase capability and the current drive capability without anyneed for a specific element (for example, high withstand voltage MOStransistor) or a specific manufacturing process. Therefore, anirreversible nonvolatile semiconductor memory device using a gate oxidefilm destruction type anti-fuse element can be easily provided.

FIG. 5 shows further another example of a configuration of a Dicksontype charge pump. This Dickson type charge pump is shown for the purposeof comparison with the Dickson type charge pump in accordance with thefirst embodiment of the present invention shown in FIG. 2. The presentexample describes a case in which a contrivance for improving a currentdrive capability has been made in a Dickson type charge pump configuredusing a P-type MOS transistor.

In the contrivance for improving the current drive capability, gates offive P-type MOS transistors 152 ₋₁, 152 ₋₂, 152 ₋₃, 152 ₋₄, and 152 ₋₅connected in series are controlled by means of rectangular wave clocksignals Φ1′ and Φ2′ that are VSS on the low electric potential side andare VPP at the high electric potential side, alternately, whereby areliable cutoff state and a sufficient ON current can be obtained. Theclock signals Φ1′ and Φ2′ are synchronized with the clock signals Φ1 andΦ2 for driving the pumping capacitors C1, C2, C3, and C4. For example,these clock signals are generated by means of a clock signal generatingcircuit 15 c.

In the case where such a configuration is provided, in this Dickson typecharge pump 152, gate withstand voltages of the P-type MOS transistors152 ₋₁, 152 ₋₂, 152 ₋₃, 152 ₋₄, and 152 ₋₅ become a problem. That is,the gates of the P-type MOS transistors 152 ₋₁, 152 ₋₂, 152 ₋₃, 152 ₋₄,and 152 ₋₅ are controlled by means of the clock signals Φ1′ and Φ2′ thatare VSS at the low electric potential side. Therefore, in particular, avoltage increase output power source VPP that is a high electricpotential is applied as it is to the P-type MOS transistor 152 ₋₅ at afinal stage. In the case of an irreversible nonvolatile semiconductormemory device using a gate oxide film destruction type anti-fuseelement, the voltage increase output power source VPP is such a highvoltage that the gate oxide films of the P-type MOS transistors 152 ₋₁,152 ₋₂, 152 ₋₃, 152 ₋₄, and 152 ₋₅ can be destructed within a shorttime. Therefore, in the irreversible nonvolatile semiconductor memorydevice using the gate oxide film destruction type anti-fuse element, ahigh withstand voltage MOS transistor is required in order for thisDickson type charge pump 152 to be applicable. In this case, theirreversible nonvolatile semiconductor memory device using the gateoxide film destruction type anti-fuse element cannot be inexpensivelyprovided.

In contrast, in the case of the Dickson type charge pump (15) inaccordance with the first embodiment of the present invention shown inFIG. 2, the intermediate electric potentials (gate signals G1, G2, G3,G4, and G5) of the gate voltages for controlling gates of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ are generated by meansof the dynamic level converter circuits 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b₋₄, and 15 b ₋₅. In this manner, even in the Dickson type charge pumpusing the P-type MOS transistor, it becomes possible to improve thecurrent drive capability without any need for a specific element (forexample, high withstand voltage MOS transistor) or a specificmanufacturing process. Therefore, the irreversible nonvolatilesemiconductor memory device using the gate oxide film destruction typeanti-fuse element can be inexpensively provided.

In the case of the Dickson type charge pump (15) in accordance with thefirst embodiment described above, it is possible to configure thepumping capacitors Ca1, Ca2, Ca3, and Ca4 and the auxiliary pumpingcapacitors Cb1, Cb2, Cb3, Cb4, and Cb5 so as to be driven by means ofthe clock signals Φ1′ and Φ2′ synchronized with the clock signals Φ1 andΦ2.

In addition, without being limited to the P-type MOS transistor, forexample, as shown in FIG. 6, it is possible to configure a negativevoltage increase charge pump (Dickson type charge pump) 15′ forgenerating a negative voltage increase output power source (electricpotential) VBB by connecting the N-type MOS transistors 15′₋₁, 15′₋₂,15′₋₃, 15′₋₄, and 15′₋₅ in series. In the case of this negative voltageincrease charge pump 15′ as well, it is possible to configure thepumping capacitors Ca1, Ca2, Ca3, and Ca4 and the auxiliary pumpingcapacitors Cb1, Cb2, Cb3, Cb4, and Cb5 so as to be driven by means ofthe clock signals Φ1′ and Φ2′ synchronized with the clock signals Φ1 andΦ2.

In any configuration, it is possible to use N-type MOS transistors orP-type MOS transistors in place of the resistor elements R1, R2, R3, R4,and R5.

Second Embodiment

FIG. 7 shows an example of a configuration of a Dickson type charge pumpin accordance with a second embodiment of the present invention. Thepresent embodiment also describes a Dickson type charge pump suitablefor use as a voltage increase charge pump in an irreversible nonvolatilesemiconductor memory device using a gate oxide film destruction typeanti-fuse element. In addition, the present embodiment describes anexample of a Dickson type charge pump having a five-stage structure inwhich five P-type MOS transistors serving as current rectifier elementsare connected in series. Like constituent elements of the Dickson typecharge pump shown in FIG. 2 are designated by like reference numerals. Adetailed description thereof is omitted here.

This Dickson type charge pump 15A is provided as an example in whichback gate bias circuits 154 ₋₁, 154 ₋₂, 154 ₋₃, 154 ₋₄, and 154 ₋₅ havebeen added to the Dickson type charge pump having the configurationshown in FIG. 2, for providing an electric potential to an N-well thatis a back gate of each of P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15₋₄, and 15 ₋₅. In the case of the present embodiment, one electrode ofan auxiliary pumping capacitor Cb0 is connected via a resistor elementR0 to a node V0 between an external supply power source VDD and theP-type MOS transistor 15 ₋₁. A first clock signal Φ1 from a first clocksignal generator unit 15 a ₋₁ is applied to the other electrode of thisauxiliary pumping capacitor Cb0.

The back gate bias circuits 154 ₋₁, 154 ₋₂, 154 ₋₃, 154 ₋₄, and 154 ₋₅are composed of two serially connected P-type MOS transistors 154 a ₋₁and 154 b ₋₁, 154 a ₋₂ and 154 b ₋₂, 154 a ₋₃ and 154 b ₋₃, 154 a ₋₄ and154 b-4, and 154 a ₋₅ and 154 b ₋₅, respectively. One P-type MOStransistors 154 a ₋₁, 154 a ₋₂, 154 a ₋₃, 154 a ₋₄, and 154 a ₋₅ connectbetween each of nodes V0, V1, V2, V3, and V4 of the source side of theP-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ and each ofback gates B1, B2, B3, B4, and B5. The other P-type MOS transistors 154b ₋₁, 154 b ₋₂, 154 b ₋₃, 154 b ₋₄, and 154 b ₋₅ connect between each ofnodes V1, V2, V3, V4, and V5 of the drain side of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ and each of the backgates B1, B2, B3, B4, and B5.

Here, with reference to the P-type MOS transistor 15 ₋₂ at the secondstage, a description will be given with respect to an operation of theback gate bias circuit 154 ₋₂. First, let us consider a case in which aclock signal Φ2 is a high electric potential VDD and a clock signal Φ1is a low electric potential VSS. At this time, the electric potential ofthe node V1 at the source side of the P-type MOS transistor 15 ₋₂ ishigher than the electric potential of the node V2 at the drain side. Inaddition, in order for the P-type MOS transistor 15 ₋₂ to beelectrically conductive, a gate signal G2 supplied to the gate thereofbecomes a low electric potential. This gate signal G2 is also suppliedto a gate of the P-type MOS transistor 154 a ₋₂ configuring the backgate bias circuit 154 ₋₂. In this manner, the P-type MOS transistor 154a ₋₂ becomes electrically conductive. Concurrently, the electricpotential of the back gate B2 becomes equal to that of the node V1 atthe source side that is the highest electric potential at this time.

Next, let us consider a case in which a clock signal Φ1 is a highelectric potential VDD and a clock signal Φ2 is a low electric potentialVSS. At this time, the electric potential of the node V2 at the drainside of the P-type MOS transistor 15 ₋₂ is higher than the electricpotential of the node V1 at the source side. In addition, in order forthe P-type MOS transistor 15 ₋₂ to be electrically nonconductive, a gatesignal G2 supplied to the gate thereof becomes a high electricpotential. This gate signal G2 is also supplied to a gate of the P-typeMOS transistor 154 a ₋₂ configuring the back gate bias circuit 154 ₋₂.In this manner, the P-type MOS transistor 154 a ₋₂ becomes electricallynonconductive. At this time, in order for the previous-stage P-type MOStransistor 15 ₋₁ to be electrically conductive, the gate signal G1thereof becomes a low voltage. This gate signal G1 is also supplied to agate of the P-type MOS transistor 154 b ₋₂ configuring the targetsecond-stage back gate bias circuit 154 ₋₂. In this manner, the P-typeMOS transistor 154 b ₋₂ becomes electrically conductive. Concurrently,the electric potential of the back gate B2 becomes equal to that of thenode V2 at the drain side that is the highest electric potential at thistime.

Such an operation is repeated for the respective P-type MOS transistors15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅. Assuming that the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ are formed on a P-typesubstrate, the electric potential of the N-well serving as the back gatethereof is always maintained at a higher electric potential that that ofa P+ type diffusion region serving as a source and a drain. In thismanner, the generation of a forward current of a PN junction formed ofthe N-well and the P+ type diffusion region can be prevented. Namely,there are attained an advantageous effect of preventing the generationof a leak current onto a substrate due to an operation of a parasiticbipolar and an advantageous effect of preventing a danger of latch-up.

In addition, it is possible to prevent the respective N-wells frombecoming a higher electric potential than necessary. This causes anadvantageous effect of preventing a phenomenon that threshold voltagesof the P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅increase, and then, an ON current decreases. Namely, according to theDickson type charge pump 15A of the present embodiment, there can beprovided an internal voltage increase power source (voltage increasecharge pump 15) that has a high current supply capability and thatoperates stably. Therefore, even with the Dickson type charge pump 15Ausing a P-type MOS transistor for a current rectifier element, it ispossible to inexpensively provide an irreversible nonvolatilesemiconductor memory device using a gate oxide film destruction typeanti-fuse element without any need for a specific element (for example,high withstand voltage MOS transistor) or a specific manufacturingprocess.

In the case of this Dickson type charge pump 15A as well, it is possibleto configure pumping capacitors Ca1, Ca2, Ca3, and Ca4 and auxiliarypumping capacitors Cb0, Cb1, Cb3, Cb4, and Cb5 so as to be driven bymeans of clock signals Φ1′ and Φ2′ synchronized with clock signals Φ1and Φ2.

In addition, it is possible to configure a negative Dickson type chargepump using an N-type MOS transistor.

In addition, in any configuration, it is possible to use N-type MOStransistors or P-type transistors in place of resistor elements R1, R2,R3, R4, and R5.

Third Embodiment

FIG. 8 shows an example of a configuration of a charge pump inaccordance with a third embodiment of the present invention. The presentembodiment describes a charge pump suitable for use as a voltageincrease charge pump in an irreversible nonvolatile semiconductor memorydevice using a gate oxide film destruction type anti-fuse element. Inaddition, the present embodiment describes an example in which a Dicksontype charge pump having a five-stage structure in which five P-type MOStransistors serving as current rectifier elements are connected inseries is prepared in two systems, and gate signals of the P-type MOStransistors in the respective systems are cross-coupled with each other.Like constituent elements of the Dickson type charge pump shown in FIG.7 are designated by like reference numerals. A detailed descriptionthereof is omitted here.

For example, this charge pump 15B includes: a Dickson type charge pump15B₋₁ of a first system and a Dickson type charge pump 15B₋₂ of a secondsystem having a substantially similar configuration to that of the firstsystem. In addition, this charge pump 15B reversibly supplies first andsecond clock signals Φ1 and Φ2 for driving a pumping capacitor in eachone of the systems (15B₋₁ and 15B₋₂). That is, in the Dickson typecharge pump 15B₋₁ of the first system, the first clock signal Φ1 issupplied to pumping capacitors Ca2 and Ca4 and auxiliary pumpingcapacitors Cb2 and Cb4, respectively. In addition, the second signal Φ2is supplied to pumping capacitors Ca1 and Ca3 and auxiliary pumpingcapacitors Cb1, Cb3 and Cb5, respectively. On the other hand, in theDickson type charge pump 15B₋₂ of the second system, the first clocksignal Φ1 is supplied to pumping capacitors Ca1′ and Ca3′ and auxiliarypumping capacitors Cb1′, Cb3′, and Cb5′, respectively. In addition, thesecond clock signal Φ2 is supplied to pumping capacitors Ca2′ and Ca4′and auxiliary pumping capacitors Cb2′ and Cb4′, respectively.

In addition, a configuration of a dynamic level converter circuit isalso different from that of the Dickson type charge pump 15A shown inthe second embodiment. That is, in the Dickson type charge pump 15B₋₁ ofthe first system, one end of each of resistor elements R1, R2, R3, R4,and R5 configuring the dynamic level converter circuits (correspondingto 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and 15 b ₋₅ of FIG. 7) isconnected to each of nodes V0′, V1′, V2′, V3′, and V4′ at the sourceside of the P-type MOS transistors 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and15 ₅′ in the Dickson type charge pump 15B₋₂ of the second system. On theother hand, in the Dickson type charge pump 15B₋₂ of the second system,one end of each of resistor elements R1′, R2′, R3′, R4′, and R5′configuring the dynamic level converter circuit is connected to each ofnodes V0, V1, V2, V3, and V4 at the source side of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅.

In addition, in the Dickson type charge pump 15B₋₁ of the first system,a resistor element R0 is connected between a gate of the P-type MOStransistor 15 ₋₁ and a power source VSS at the low electric potentialside. Similarly, in the Dickson type charge pump 15B₋₂ of the secondsystem, a resistor element R0′ is connected between a gate of the P-typeMOS transistor 15 ₋₁′ and a power source VSS at the low electricpotential side.

FIGS. 9A to 9E each show an operating waveform of a charge pump 15Bhaving the configuration described above. Here, FIGS. 9A to 9E each showa relationship among outputs (gate signals) G1, G2, G3, G4, and G5 ofdynamic level converter circuits of the Dickson type charge pump 15B₋₁of the first system; electric potentials of nodes V1, V2, V3, and V4 ofthe P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅; and anexternal supply power source VDD and a voltage increase output powersource VPP. Each horizontal axis denotes a time (t) and each verticalaxis denotes an electric potential (V).

As is evident from FIGS. 9A to 9E, in the case of the third embodiment,it is found that the electric potentials of the gate signals G1, G2, G3,G4, and G5 indicated by the dashed line are wholly lowered as comparedwith the operating waveforms in the case of the first embodimentdescribed above (refer to FIGS. 3A to 3E). This is because, in the firstand second embodiments, one end of each of the resistor elements R1, R2,R3, R4, and R5 configuring the dynamic level converter circuits 15 b ₋₁,15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and 15 b ₋₅ is connected to each of nodes V1,V2, V3, V4, and V5 at the drain side of the P-type MOS transistors 15₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively, while in the thirdembodiment, one end of each of the resistor elements R1, R2, R3, R4, andR5 and R1′, R2′, R3′, R4′, and R5′ is connected to each of nodes V0, V1,V2, V3, and V4 and V0′, V1′, V2′, V3′, and V4′ at the source side of theP-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ and 15 ₋₁′,15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′.

In addition, in the dynamic level converter circuit at the first stage,resistor elements R0 and R0′ are added between a gate of each of theP-type MOS transistors 15 ₋₁ and 15 ₋₁′ and the power source VSS at thelow electric potential side. In this manner, an average electricpotential of the gate signals G1 and G1′ at the first stage is set to belower than the power source VDD at the high electric potential side.Namely, the electric potentials of gate signals G1, G2, G3, G4, and G5and G1′, G2′, G3′, G4′, and G5′ can be set to be lower, whereby thecurrent drive capabilities of the P-type MOS transistors 15 ₋₁, 15 ₋₂,15 ₋₃, 15 ₋₄, and 15 ₋₅ and 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′can be enhanced.

In this way, according to the third embodiment described above, a chargepump 15B having a high current drive capability can be achieved.Therefore, this charge pump 15B is applied as a voltage increase chargepump 15, thereby enabling high performance of an irreversiblenonvolatile semiconductor memory device using a gate oxide filmdestruction type anti-fuse element.

In the case of this charge pump 15B, it is possible to configure pumpingcapacitors Ca1, Ca2, Ca3, and Ca4 and Ca1′, Ca2′, Ca3′, and Ca4′ andauxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5 and Cb1′, Cb2′,Cb3′, Cb4′, and Cb5′ so as to be driven by means of clock signals Φ1′and Φ2′ synchronized with the clock signals Φ1 and Φ2.

In addition, it is also possible to configure a negative charge pumpusing an N-type MOS transistor.

Fourth Embodiment

FIG. 10 shows an example of a configuration of a charge pump inaccordance with a fourth embodiment of the present invention. Thepresent embodiment describes a charge pump suitable for use as a voltageincrease charge pump in an irreversible nonvolatile semiconductor memorydevice using a gate oxide film destruction type anti-fuse element. Inaddition, the present embodiment describes an example in which a Dicksontype charge pump having a five-stage structure in which five P-type MOStransistors serving as current rectifier elements are connected inseries is prepared in two systems, and gate signals of the P-type MOStransistors in the respective systems are cross-coupled with each other.Like constituent elements of the Dickson type charge pump shown in FIG.8 are designated by like reference numerals. A detailed descriptionthereof is omitted here.

In the fourth embodiment, each of the resistor elements of the chargepump in the third embodiment described above is replaced by an N-typeMOS transistor. That is, in this charge pump 15C, the dynamic levelconverter circuits in a Dickson type charge pump 15C₋₁ of a first system(corresponding to 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and 15 b ₋₅ ofFIG. 7) are configured of: resistor units Ra1, Ra2, Ra3, Ra4, and Ra5each consisting of three N-type MOS transistors NMa, NMb, and NMc; andauxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5. Similarly, thedynamic level converter circuits in a Dickson type charge pump 15C₋₂ ofa second system (corresponding to 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄,and 15 b ₋₅ of FIG. 7) are configured of: resistor units Ra1′, Ra2′,Ra3′, Ra4′, and Ra5′ each consisting of three N-type MOS transistorsNMa′, NMb′, and NMc′; and auxiliary pumping capacitors Cb1′, Cb2′, Cb3′,Cb4′, and Cb5′.

In addition, in the dynamic level converter circuit of the first stage,resistor units NM0 and NM0′ each consisting of an N-type MOS transistorare connected between a gate of each of the P-type MOS transistors 15 ₋₁and 15 ₋₁′ and the power source VSS at the low electric potential side,respectively.

The dynamic level converter circuits in the Dickson type charge pump15C₋₁ of the first system each branch a slight electric charge from eachof the nodes V0, V1, V2, V3, and V4 at the source side of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively, andstores the branched electric charge in the auxiliary pumping capacitorsCb1, Cb2, Cb3, Cb4, and Cb5. In this manner, an average electricpotential of the gate signals G1, G2, G3, G4, and G5 is compensated for,namely, is set at an optimal value. Similarly, the dynamic levelconverter circuits in the Dickson type charge pump 15C₋₂ of the secondsystem each branch a slight electric charge from each of the nodes V0′,V1′, V2′, V3′, and V4′ at the source side of the P-type MOS transistors15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′, respectively, and stores thebranched electric charge in the auxiliary pumping capacitors Cb1′, Cb2′,Cb3′, Cb4′, and Cb5′. In this manner, an average electric potential ofthe gate signals G1′, G2′, G3′, G4′, and G5′ is compensated for, namely,is set at an optimal value.

In the case where such a configuration is provided, electricalcharacteristics expected by the dynamic level converter circuits aresubstantially equivalent to those of resistor elements of about 15 KΩ,and characteristic degradations such as decrease of an ON current andincrease of a cutoff current never cause a problem in particular. Inaddition, as long as gate oxide film destruction type anti-fuse elements13 a to 13 d enter a high resistance conductive state at the time of aninformation write operation, an irreversible nonvolatile semiconductormemory device using a gate oxide film destruction type anti-fuse elementmay have any configuration, and thus, a variety of embodiments can beconceived.

Moreover, according to the fourth embodiment, a process formanufacturing a resistor element can be eliminated. Therefore, anirreversible nonvolatile semiconductor memory device using a gate oxidefilm destruction type anti-fuse element can be achieved moreinexpensively.

In the case of this charge pump 15C as well, it is possible to configurepumping capacitors Ca1, Ca2, Ca3, and Ca4 and Ca1′, Ca2′, Ca3′, and Ca4′and auxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5 and Cb1′,Cb2′, Cb3′, Cb4′, and Cb5′ so as to be driven by means of clock signalsΦ1′ and Φ2′ synchronized with the clock signals Φ1 and Φ2.

In addition, it is also possible to configure a negative charge pumpusing an N-type MOS transistor.

Fifth Embodiment

FIG. 11 shows an example of a configuration of a charge pump inaccordance with a fifth embodiment of the present invention. The presentembodiment describes a charge pump suitable for use as a voltageincrease charge pump in an irreversible nonvolatile semiconductor memorydevice using a gate oxide film destruction type anti-fuse element. Inaddition, the present embodiment describes an example in which a Dicksontype charge pump having a five-stage structure in which five P-type MOStransistors serving as current rectifier elements are connected inseries is prepared in two systems, and gate signals of the P-type MOStransistors in the respective systems are cross-coupled with each other.Like constituent elements of the charge pump shown in FIG. 8 aredesignated by like reference numerals. A detailed description thereof isomitted here.

In the fifth embodiment, each of the resistor elements of the chargepump in the third embodiment described above is replaced by a P-type MOStransistor. That is, in this charge pump 15D, the dynamic levelconverter circuits in a Dickson type charge pump 15D₋₁ of a first system(corresponding to 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and 15 b ₋₅ ofFIG. 7) are configured of: P-type MOS transistors 154 c ₋₁, 154 c ₋₂,154 c ₋₃, 154 c ₋₄, and 154 c ₋₅ which function as resistor elements;and auxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5,respectively. In the P-type MOS transistors 154 c ₋₁, 154 c ₋₂, 154 c₋₃, 154 c ₋₄, and 154 c ₋₅, gates are connected to gates of the P-typeMOS transistors 154 a ₋₁, 154 a ₋₂, 154 a ₋₃, 154 a ₋₄, and 154 a ₋₅ andthe P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅,respectively. One electrode of each of the auxiliary pumping capacitorsCb1, Cb2, Cb3, Cb4, and Cb5 is connected to each gate of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively. One ofthe source and the drain of each of the P-type MOS transistors 154 c ₋₁,154 c ₋₂, 154 c ₋₃, 154 c ₋₄, and 154 c ₋₅ is connected to each of nodesV0, V1, V2, V3, and V4 at the source of the P-type MOS transistors 15₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively. The other one of thesource and the drain of each of the P-type MOS transistors 154 c ₋₁, 154c ₋₂, 154 c ₋₃, 154 c ₋₄, and 154 c ₋₅ is connected to each gate of theP-type MOS transistors 154 b ₋₁, 154 b ₋₂, 154 b ₋₃, 154 b ₋₄, and 154 b₋₅.

In addition, a back gate of the P-type MOS transistor 154 c ₋₁ isconnected to each back gate B1 of the P-type MOS transistors 15 ₋₁, 154a ₋₁, and 154 b ₋₁. A back gate of the P-type MOS transistor 154 c ₋₂ isconnected to each back gate B2 of the P-type MOS transistors 15 ₋₂, 154a ₋₂, and 154 b ₋₂. A back gate of the P-type MOS transistor 154 c ₋₃ isconnected to each back gate B3 of the P-type MOS transistors 15 ₋₃, 154a ₋₃, and 154 b ₋₃. A back gate of the P-type MOS transistor 154 c ₋₄ isconnected to each back gate B4 of the P-type MOS transistors 15 ₋₄, 154a ₋₄, and 154 b ₋₄. A back gate of the P-type MOS transistor 154 c ₋₅ isconnected to each back gate B5 of the P-type MOS transistors 15 ₋₅, 154a ₋₅, and 154 b ₋₅.

Similarly, the dynamic level converter circuits in a Dickson type chargepump 15D₋₂ of a second system (corresponding to 15 b ₋₁, 15 b ₋₂, 15 b₋₃, 15 b ₋₄, and 15 b ₋₅ of FIG. 7) are configured of: P-type MOStransistors 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′which function as resistor elements; and auxiliary pumping capacitorsCb1′, Cb2′, Cb3′, Cb4′, and Cb5′, respectively. In the P-type MOStransistors 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′,gates are connected to gates of the P-type MOS transistors 154 a ₋₁′,154 a ₋₂′, 154 a ₋₃′, 154 a ₋₄′, and 154 a ₋₅′ and the P-type MOStransistors 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′, respectively.One electrode of each of the auxiliary pumping capacitors Cb1′, Cb2′,Cb3′, Cb4′, and Cb5′ is connected to each gate of the P-type MOStransistors 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′, respectively.One of the source and the drain of each of the P-type MOS transistors154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′, is connectedto each of nodes V0′, V1′, V2′, V3′, and V4′ at the source of the P-typeMOS transistors 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′. The otherone of the source and the drain of each of the P-type MOS transistors154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′ is connectedto each gate of the P-type MOS transistors 154 b ₋₁′, 154 b ₋₂′, 154 b₋₃′, 154 b ₋₄′, and 154 b ₋₅′, respectively.

In addition, a back gate of the P-type MOS transistor 154 c ₋₁′ isconnected to each back gate B1′ of the P-type MOS transistors 15 ₋₁′,154 a ₋₁′, and 154 b ₋₁′. A back gate of the P-type MOS transistor 154 c₋₂′ is connected to each back gate B2′ of the P-type MOS transistors 15₋₂′, 154 a ₋₂′, and 154 b ₋₂′. A back gate of the P-type MOS transistor154 c ₋₃′ is connected to each back gate B3′ of the P-type MOStransistors 15 ₋₃′, 154 a ₋₃′, and 154 b ₋₃′. A back gate of the P-typeMOS transistor 154 c ₋₄′ is connected to each back gate B4′ of theP-type MOS transistors 15 ₋₄′, 154 a ₋₄′, and 154 b ₋₄′. A back gate ofthe P-type MOS transistor 154 c ₋₅′ is connected to each back gate B5′of the P-type MOS transistors 15 ₋₅′, 154 a ₋₅′, and 154 b ₋₅′.

The dynamic level converter circuits in the Dickson type charge pump15D₋₁ of the first system each branch a slight electric charge from eachof the nodes V0, V1, V2, V3, and V4 at the source side of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively, andstores the branched electric charge in the auxiliary pumping capacitorsCb1, Cb2, Cb3, Cb4, and Cb5. In this manner, an average electricpotential of the gate signals G1, G2, G3, G4, and G5 is compensated for,namely, is set at an optimal value. Similarly, the dynamic levelconverter circuits in the Dickson type charge pump 15D₋₂ of the secondsystem each branch a slight electric charge from each of the nodes V0′,V1′, V2′, V3′, and V4′ at the source side of the P-type MOS transistors15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′, respectively, and stores thebranched electric charge in the auxiliary pumping capacitors Cb1′, Cb2′,Cb3′, Cb4′, and Cb5′. In this manner, an average electric potential ofthe gate signals G1′, G2′, G3′, G4′, and G5′ is compensated for, namely,is set at an optimal value.

In the case where such a configuration is provided, the resistorelements configuring a dynamic level converter circuit can be replacedby single P-type MOS transistors 154 c ₋₁, 154 c ₋₂, 154 c ₋₃, 154 c ₋₄,and 154 c ₋₅ and 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c₋₅′, respectively. Therefore, it becomes possible to reduce a processcost more remarkably, for example, to eliminate a process formanufacturing a resistor element. Hence, an irreversible nonvolatilesemiconductor memory device using a gate oxide film destruction typeanti-fuse element can be achieved more inexpensively.

In addition, a gate to source voltage, a gate to drain voltage, and asource to drain voltage each are equal to that of an external supplypower source VDD at most, the voltages being applied to all of theP-type MOS transistors configuring this charge pump 15D. Thus, elementreliability can be fully allocated.

Further, in all of the P-type MOS transistors, the electric potentialsof the back gates B1, B2, B3, B4, and B5 and B1′, B2′, B3′, B4′, and B5′become always high electric potentials as compared with the electricpotentials of the nodes V0, V1, V2, V3, V4, and V5 and V0′, V1′, V2′,V3′, V4′, and V5′ at the source side and at the drain side of therespective transistors. Therefore, there is no danger that a latch-upoccurs. In contrast, in all of the P-type MOS transistors, the electricpotentials of the back gates B1, B2, B3, B4, and B5 and B1′, B2′, B3′,B4′, and B5′ never become an extremely high electric potential ascompared with the electric potentials of the nodes V0, V1, V2, V3, V4,and V5 and V0′, V1′, V2′, V3′, V4′, and V5′ at the source side and atthe drain side of the respective transistors. Thus, the current drivecapability of the P-type MOS transistors is never lowered due to theinfluence of a back gate effect.

In this manner, according to the fifth embodiment described above, thecurrent drive capabilities of the P-type MOS transistors 15 ₋₁, 15 ₋₂,15 ₋₃, 15 ₋₄, and 15 ₋₅ and 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′can be improved. Therefore, it becomes possible to increase a supplycurrent of this charge pump 15D. This effect is particularly significantin the case where the threshold voltage of the P-type MOS transistor ishigh.

In the case of this charge pump 15D as well, it is possible to configurepumping capacitors Ca1, Ca2, Ca3, and Ca4 and Ca1′, Ca2′, Ca3′, and Ca4′and auxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5 and Cb1′,Cb2′, Cb3′, Cb4′, and Cb5′ so as to be driven by means of clock signalsΦ1′ and Φ2′ synchronized with the clock signals Φ1 and Φ2.

In addition, it is possible to configure a negative charge pump using anN-type MOS transistor.

Sixth Embodiment

FIG. 12 shows an example of a configuration of a charge pump inaccordance with a sixth embodiment of the present invention. The presentembodiment also describes a charge pump suitable for use as a voltageincrease charge pump in an irreversible nonvolatile semiconductor memorydevice using a gate oxide film destruction type anti-fuse element. Inaddition, the present embodiment describes an example in which a Dicksontype charge pump having a five-stage structure in which five P-type MOStransistors serving as current rectifier elements are connected inseries is prepared in two systems, and gate signals of the P-type MOStransistors in the respective systems are cross-coupled with each other.Like constituent elements of the charge pump shown in FIG. 11 aredesignated by like reference numerals. A detailed description thereof isomitted here.

According to the sixth embodiment, an inlet port of an electric chargefor compensating for an average electric potential of dynamic levelconverter circuits (gate signals), of the charge pump 15D in the fifthembodiment described above, is changed from each of the nodes at thesource side of the P-type MOS transistor (current rectifier element) toeach of the nodes at the drain side. That is, in this charge pump 15E,dynamic level converter circuits in a Dickson type charge pump 15E₋₁ ofa first system (corresponding to 15 b ₋₁, 15 b ₋₂, 15 b ₋₃, 15 b ₋₄, and15 b ₋₅ of FIG. 7) are composed of P-type MOS transistors 154 c ₋₁, 154c ₋₂, 154 c ₋₃, 154 c ₋₄, and 154 c ₋₅ serving as resistor elements andauxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5, respectively.In the P-type MOS transistors 154 c ₋₁, 154 c ₋₂, 154 c ₋₃, 154 c ₋₄,and 154 c ₋₅, gates are connected to gates of the P-type MOS transistors154 b ₋₁, 154 b ₋₂, 154 b ₋₃, 154 b ₋₄, and 154 b ₋₅. One of the sourceand the drain of each of the P-type MOS transistors 154 c ₋₁, 154 c ₋₂,154 c ₋₃, 154 c-4, and 154 c ₋₅ is connected to each gate of the P-typeMOS transistors 154 a ₋₁, 154 a ₋₂, 154 a ₋₃, 154 a ₋₄, and 154 a ₋₅ andeach gate of the P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and15 ₋₅. One electrode of each of the above auxiliary pumping capacitorsCb1, Cb2, Cb3, Cb4, and Cb5 is connected to each gate of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅. The other one of thesource and the drain of each of the P-type MOS transistors 154 c ₋₁, 154c ₋₂, 154 c ₋₃, 154 c ₋₄, and 154 c ₋₅ is connected to each of nodes V1,V2, V3, V4, and V5 at the drain side of the P-type MOS transistors 15₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively.

In addition, a back gate of the P-type MOS transistor 154 c ₋₁ isconnected to each back gate B1 of the P-type MOS transistors 15 ₋₁, 154a ₋₁, and 154 b ₋₁. A back gate of the P-type MOS transistor 154 c ₋₂ isconnected to each back gate B2 of the P-type MOS transistors 15 ₋₂, 154a ₋₂, and 154 b ₋₂. A back gate of the P-type MOS transistor 154 c ₋₃ isconnected to each back gate B3 of the P-type MOS transistors 15 ₋₃, 154a ₋₃, and 154 b ₋₃. A back gate of the P-type MOS transistor 154 c ₋₄ isconnected to each back gate B4 of the P-type MOS transistors 15 ₋₄, 154a ₋₄, and 154 b ₋₄. A back gate of the P-type MOS transistor 154 c ₋₅ isconnected to each back gate B5 of the P-type MOS transistors 15 ₋₅, 154a ₋₅, and 154 b ₋₅.

Similarly, the dynamic level converter circuits in a Dickson type chargepump 15E₋₂ of a second system (corresponding to 15 b ₋₁, 15 b ₋₂, 15 b₋₃, 15 b ₋₄, and 15 ₋₅ of FIG. 7) are composed of: P-type MOStransistors 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′that function as resistor elements and auxiliary pumping capacitorsCb1′, Cb2′, Cb3′, Cb4′, and Cb5′, respectively. In the P-type MOStransistors 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′,gates are connected to gates of the P-type MOS transistors 154 b ₋₁′,154 b ₋₂′, 154 b ₋₃′, 154 b ₋₄′, and 154 b ₋₅′. One of the source andthe drain of the P-type MOS transistors 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′,154 c ₋₄′, and 154 c ₋₅′ is connected to each gate of the P-type MOStransistors 154 a ₋₁′, 154 a ₋₂′, 154 a ₋₃′, 154 a ₋₄′, and 154 a ₋₅′and each gate of the P-type MOS transistors 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15₋₄′, and 15 ₋₅′, respectively. One electrode of each of the aboveauxiliary pumping capacitors Cb1′, Cb2′, Cb3′, Cb4′, and Cb5′ isconnected to each gate of the P-type MOS transistors 15 ₋₁′, 15 ₋₂′, 15₋₃′, 15 ₋₄′, and 15 ₋₅′. The other one of the source and the drain ofeach of the P-type MOS transistors 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154c ₋₄′, and 154 c ₋₅′ is connected to each of nodes V1′, V2′, V3′, V4′,and V5′ at the drain side of the P-type MOS transistors 15 ₋₁′, 15 ₋₂′,15 ₋₃′, 15 ₋₄′, and 15 ₋₅′.

In addition, a back gate of the P-type MOS transistor 154 c ₋₁ isconnected to each back gate B1′ of the P-type MOS transistors 151 ₋₁′,154 a ₋₁′, and 154 b ₋₁′. A back gate of the P-type MOS transistor 154 c₋₂′ is connected to each back gate B2′ of the P-type MOS transistors 15₋₂′, 154 a ₋₂′, and 154 b ₋₂′. A back gate of the P-type MOS transistor154 c ₋₃′ is connected to each back gate B3′ of the P-type MOStransistors 15 ₋₃′, 154 a ₋₃′, and 154 b ₋₃′. A back gate of the P-typeMOS transistor 154 c ₋₄′ is connected to each back gate B4′ of theP-type MOS transistors 15 ₋₄′, 154 a ₋₄′, and 154 b ₋₄′. A back gate ofthe P-type MOS transistor 154 c ₋₅′ is connected to each back gate B5′of the P-type MOS transistors 15 ₋₅′, 154 a ₋₅′, and 154 b ₋₅′.

The dynamic level converter circuits in the Dickson type charge pump15E₋₁ of the first system each branch a slight electric charge from eachof the nodes V1, V2, V3, V4, and V5 at the drain side of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅, respectively, andstores the branched electric charge in the auxiliary pumping capacitorsCb1, Cb2, Cb3, Cb4, and Cb5. In this manner, an average electricpotential of the gate signals G1, G2, G3, G4, and G5 is compensated for,namely, is set at an optimal value. Similarly, the dynamic levelconverter circuits in the Dickson type charge pump 15E₋₂ of the secondsystem each branch a slight electric charge from each of the nodes V1′,V2′, V3′, V4′, and V5′ at the drain side of the P-type MOS transistors15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′, respectively, and stores thebranched electric charge in the auxiliary pumping capacitors Cb1′, Cb2′,Cb3′, Cb4′, and Cb5′. In this manner, an average electric potential ofthe gate signals G1′, G2′, G3′, G4′, and G5′ is compensated for, namely,is set at an optimal value.

In the case where such a configuration is provided as well, advantageouseffect substantially similar to that in the case of the fifth embodimentdescribed previously can be attained. That is, the resistor elementsconfiguring a dynamic level converter circuit can be replaced by singleP-type MOS transistors 154 c ₋₁, 154 c ₋₂, 154 c ₋₃, 154 c ₋₄, and 154 c₋₅ and 154 c ₋₁′, 154 c ₋₂′, 154 c ₋₃′, 154 c ₋₄′, and 154 c ₋₅′,respectively. Therefore, it becomes possible to reduce a process costmore remarkably, for example, to eliminate a process for manufacturing aresistor element. Hence, an irreversible nonvolatile semiconductormemory device using a gate oxide film destruction type anti-fuse elementcan be achieved more inexpensively.

Moreover, the inlet ports of electric charges of the dynamic levelconverter circuits are defined as nodes V1, V2, V3, V4, and V5 and V1′,V2′, V3′, V4′, and V5′ at the drain side of the P-type MOS transistors15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ and 15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15₋₄′, and 15 ₋₅′, respectively. In this manner, the electric potentialsof the gate signals G1, G2, G3, G4, and G5 and G1′, G2′, G3′, G4′, andG5 can be set to be slightly higher than those of the gate signals G1,G2, G3, G4, and G5 and G1′, G2′, G3′, G4′, and G5′ in the case of thefifth embodiment. In this case, although the current drive capabilitiesof the P-type MOS transistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ and15 ₋₁′, 15 ₋₂′, 15 ₋₃′, 15 ₋₄′, and 15 ₋₅′ are lowered, it becomespossible to restrict a cutoff current at the time of a nonconductivestate to be small.

In this manner, according to the sixth embodiment described above, acutoff current at the time of a nonconductive state, of the P-type MOStransistors 15 ₋₁, 15 ₋₂, 15 ₋₃, 15 ₋₄, and 15 ₋₅ and 15 ₋₁′, 15 ₋₂′, 15₋₃′, 15 ₋₄′, and 15 ₋₅′, can be restricted to be small. Therefore, itbecomes possible to increase a rate of this charge pump 15E to currentconsumption, namely, to increase current efficiency. This advantageouseffect is particularly significant in the case where the thresholdvoltage of the P-type MOS transistor is low.

In the case of this charge pump 15E as well, it is possible to configurepumping capacitors Ca1, Ca2, Ca3, and Ca4 and Ca1′, Ca2′, Ca3′, and Ca4′and auxiliary pumping capacitors Cb1, Cb2, Cb3, Cb4, and Cb5 and Cb1′,Cb2′, Cb3′, Cb4′, and Cb5′ so as to be driven by means of clock signalsΦ1′ and Φ2′ synchronized with the clock signals Φ1 and Φ2.

In addition, it is possible to configure a negative charge pump using anN-type MOS transistor.

As has been described above, according to the first to sixth embodimentsof the present invention, an irreversible nonvolatile semiconductormemory device using a gate oxide film destruction type anti-fuse elementcan be achieved inexpensively.

In particular, in any of the embodiments, a pumping capacitor and anauxiliary pumping capacitor can be configured using a MOS transistor.

In addition, of course, the number of current rectifier elements is notlimited to the number of stages according to the embodiments.

Additional advantages and modifications will readily occur to thoseskilled in the art. Therefore, the invention in its broader aspects isnot limited to the specific details and representative embodiments shownand described herein. Accordingly, various modifications may be madewithout departing from the spirit or scope of the general inventiveconcept as defined by the appended claims and their equivalents.

1. A semiconductor charge pump for two systems, comprising: a pluralityof N-channel MOS (Metal Oxide Semiconductor) transistors which configurecurrent rectifier elements, respectively, said plurality of N-channelMOS transistors having gates and being connected in series between anexternal supply power source and a voltage increase output power source;a plurality of first pumping capacitors one electrode of each of whichis connected to a connection point of each of said plurality ofN-channel MOS transistors; a clock signal generating circuit whichgenerates first and second clock signals whose phases are different fromeach other by 180 degrees, the first and second clock signals beingalternately supplied from the clock signal generating circuit to theother electrodes of said plurality of first pumping capacitors; aplurality of resistor elements connected to connection points of saidplurality of N-channel MOS transistors at one end and connected to gatesof said plurality of N-channel MOS transistors at the other end; and aplurality of second pumping capacitors one electrode of each of which isconnected to the other end of each of said plurality of resistorelements, the first and second clock signals being alternately suppliedto the other electrodes of said plurality of second pumping capacitors,thereby generating control signals which control gates of said pluralityof N-channel MOS transistors, wherein, by means of the control signalgenerated by said plurality of second pumping capacitors in thesemiconductor charge pump for one system, gates of said plurality ofN-channel MOS transistors in the semiconductor charge pump for the othersystem are controlled.
 2. The semiconductor charge pump according toclaim 1, wherein said plurality of resistor elements are composed of MOStransistors, respectively.
 3. The semiconductor charge pump according toclaim 1, wherein the first and second clock signals are rectangular waveclock signals that become VSS at a low electric potential side and thatbecome VDD at a high electric potential side.
 4. The semiconductorcharge pump according to claim 1, wherein a negative voltage increasecharge pump which generates a negative voltage increase output powersource is composed of said plurality of N-channel MOS transistors. 5.The semiconductor charge pump according to claim 1, wherein saidplurality of N-channel MOS transistors have back gates, and biascircuits are connected to the back gates, respectively.
 6. Thesemiconductor charge pump according to claim 1, wherein the first andsecond clock signals are supplied in a reverse manner with respect tosaid plurality of first and second pumping a capacitors of therespective systems.